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Transcript of Tel Basics
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7/31/2019 Tel Basics
1/22
S-72.245 Transmission Methods inTelecommunication Systems (4 cr)
Noise in analog carrier wave (CW) modulationsystems
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2 Helsinki University of Technology,Communications Laboratory, Timo O. Korhonen
Noise in analog CW modulation systems
Understanding noise
Lowpass presentation of bandpass noise and its conversionto baseband noise
Noise statistics of quadrature presentation in rectangular and
polar coordinates Modeling detectors for linear and exponential modulation
Analysis of post-detection SNR
Synchronous detector
PM-detector
FM-detector
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3 Helsinki University of Technology,Communications Laboratory, Timo O. Korhonen
Noise in carrier wave modulation
systems:basic definitions
Objectives: Define bandpass noise and use it to analyze postdetection SNR of analog CW systems
Assume signal is ergodic, e.g., all ensemble averages E[] equalthe corresponding time averages . Then, for instance
where the time average is defined by
( ) E[ ( )]v t v t 2 2( ) E[ ( )]v t v t
( ) ( ) E[ ( ) ( )]v t v t v t v t
/ 2
/ 2
1( ) lim ( )
T
Ti iTv t v t dt
T
/ 2
/ 2
1( ) ( )
T
Ti iv t v t dt
T (for a known period)
or
average valueaverage power
autocorrelation
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4 Helsinki University of Technology,Communications Laboratory, Timo O. Korhonen
The system model
We consider normalized ergodic analog message whoseamplitude and power are normalized2 2
( ) 1, ( ) , 1x x
x t S x x t S Channel loss
Modulated signal
Transmitted powerReceived power
Received signal (not altered by HR)
Detector
2/R T c
S S L x
Post-detection filter
Pre-detection filter
Pre-detection noise (after HR)
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Detection models
Pre-detection signal v(t) is presented in quadrature-carrier form:
Detection models:
( ) ( )cos[ ( )]
( )cos( ) ( )cos( )
v c v
i c q c
v t A t t t
v t t v t t
( ) ( )cos ( )
( ) ( )sin ( )
i v
q v
v t A t t
v t A t t
v
( ) Synchronous detector
( ) Envelope detector( )
( ) Phase detector
( ) / Frequency detector
i
v v
v
v t
A t Ay t
t
d t dt
0 0( ) cos[ 2 ( ) ], )
t
tC C Cx t A t f x d t t
(Remember that FM was defined by:
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Pre-detection noise in bandpass channel
Signal and noise are statistically independent and therefore theirpower can be added to form the total pre-detection power:
The pre-detection (bandpass) noise power is filtered from thechannel noise:
2 2 2 c R R
v x n S N
2
0( / 2) ( ) 2 ( / 2)T
B
R R TN H f df df B
fromchannel
to detector
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Pre-detection SNR Pre-detection signal-to-noise ratio for bandpass channels is
defined by
Note that above BT is the transmission bandwidth passingchannel noise power to the detector
For comparison, we can write the received signal-to-noise interms of baseband system (BW = W) SNR defined by
and therefore also
Note that always (limiting case is the SSB with BT= W)
(We will see, however, that post detection SNR can be muchlarger than !)
/ /( )R R R T
S N S B
2
( / 2) ( )
R T RN B H f df
/( )R
S W
/ /( ) ( / )( / ) /R R R T R T T
S N S B S W W B W B
TB W /
R RS N
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Bandpass noise:
We assume stationary, zero mean Gaussian noise process forwhich
Bandpass noise in terms of lowpass equivalent signals
The in-phase and quadrature componentsare independent and hence
Their average is zero and their average power is thesame:
2 20,n R
n n N
( ) ( )cos( ) ( )sin( )i c q cn t n t t n t t
2 2 2
i q Rn n n N
( ) ( ) 0i qn t n t
0i q
n n
in
qn
nA
n
( ) ( )cos[ ( )]n c n
n t A t t t
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Bandpass noise has Rayleigh distributed
envelope and evenly distributed phase
I-Q components of the bandpass noise can be presented inenvelope - phase format:
The PDF of envelope is Rayleighdistributed defined by
Therefore mean and variance for thebandpass noise are (integrate from above, how?)
2 2 2 , arctanq
n i q n
i
nA n n
n
2 2
( ) exp ( )2n
n n
A n n
R R
A Ap A u A
N N
2 2
2
2 2 2 2
2
/ 2, 2
/ 2 ( ) / 2i q
n R n R
R n i qn n n
A N A N
N A n n n
in
qn
nA
n
Two independentr.v.:s - sum of theirvariances equals varianceof the envelope
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Post detection noise in synchronous detection
Signal component of synchronous detector:
Noise component of synchronous detector:
Detector extracts i-components and removes double frequencycomponents
( ) ( )exp( )
( ) ( )cos( ) ( )sin( )
( )( )cos( )
2( ) ( )cos(2 ) sin(2 )
2 2
DSB c
DSB c c c c
c
DSB c
c c
c c
v t x t j t
v t A x t t jA x t t
A x tv t t
A x t A x tt j t
( )cos( ) cos( ) ( )cos( ) ( )sin( )
cos(2 ) / 2 ( )si( ) 1 n(2 ) / 2
c c i c q c
ci q c
n t t t n t t n t t tn t tt n
( ) ( ) ( )D c i
y t A x t n t cos( )cos( ) 1/2 cos(2 )/ 2
cos( )sin( ) sin(2 )/ 2
x x x
x x x
detected message
received DSB signal
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Post-detection SNR for DSB
Obtain signal and noise power after detection from:
where average noise and signal power are
Received average signal power is
and therefore SNR after DSB detector is
( ) ( ) ( )D c i
y t A x t n t
2 2 2 2
( ) , ( ) D i D c c x
N n t S A x t A S
2 2 2 2 2
0
1/ 2
( ) cos ( ) / 2 2 / x
R c c x x R c
S
S A x t t A S S S A
2
2
/ /D D c D
c
xSS N A N
A
2
2R
c
S
A2 (DSB)
2 2(DSB)
T
R R R
D B WD T
S S S
WN BN
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Comparing SNR for DSB and AM
It can be show, that for AM the post detection SNR is
Comparison of this to the SNR of DSB can done by noting that
in practice
Hence AM performs usually much worse than DSB
It can be shown that for SSB performance is the same as for
DSB, e.g.
/1
x
D D AM
x
SS N
S
x
0.5 tone modulation
S 0.1 speech signal
xS
,/ R
D D USB DSB
SS N
W
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Exponential modulation and channel noise
Both PM and FM have constant envelopes so the receivedpower is constant
Received SNR is yielding for wideband FM
where for wideband modulation
2 2
( ) cos[ ( )]
/ 2
c c c
R c c
x t A t t
S x A
22
22
R c c
R R T
A
N N B
S A
1,2( 2) 2
2
mT m f W
B f W
DW
2 2
R R
R T
RS S
N B DW D
S
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Detection of exponential modulation
assuming small noise power
( )sin[ ( )]( ) arctan
( )cos[ ( )]
n n
v
c n n
A t tt
A A t t
carrier+noise
noise
( ) cos[ ( )] ( )cos[ ( )]c c n c n
Signal Noise
v t A t t A t t t
( )sin[ ( )]( ) n n
v
c
A t tt
A
small compared to Ac
Detected noise component
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Post-detection noise spectra for PM
The channel noise is bandpass noise filtered at the transmissionbandwidth and therefore the respective post-detection noise powerspectral density GPM(f) and the total noise power NDare
( )sin ( )( )
( )
2
n nv
c
q
R
A t tt A
n t
S
2
2 2
/ 2
sinR c
q n n
i q R LP
S A
n A
n n N B
2
( )( )
2
2
q
PMTR
R T
n t fG f
BS
f
S B
Note that afterdetection signalbandwidth is Wandthus a post detectionfilter is required to removeout-of-band channel noise
( ) /W
WD PM R
N G f df W S
LPB
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Post-detection SNR for FM
Recall the definition of FM-signal
Frequency discriminator (detector) differentiates theinstantaneous phase to cancel out the inherent integration inphase. Now
Inspection in frequency domain (In order to find the respectivePSDs) yields after detector
and the signal PSD is
( ) 2 ( ) ( ) / v
t x t d t dt
( )( ) 1 ( ) ( ) 1 ( )( )2 2 2 2
qv S N S
R
Signal Noise
d n td t d t d t d t x tdt dt dt dt S dt
( ) 2 ( )v
X f j f f
2
( ) ( ) ( 2FM
G f X f 22 2
) ( ) / (2 )v
f f 22
( )v
f f
0( ) cos ( ) , ( ) 2 ( )
t
c C C v v tx t A t t t f x d
( )
( 2 ) ( )
n
n
n
d x t
j f X fdt
( )( )sin ( )( )
2
qn n
vc R
n tA t tt
A S
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Post-detection SNR in FM (cont.)
Therefore, the post-detection noise PSD can be written as
and now the PSD for FM post detection noise is
and the respective total noise power is
2
( )2
FM
R T
f fG f
S B
3( ) / 3WWD FM RN G f df W S
22( ) ( )
FM vG f f f
( )( )
2
q
v
R
N ff
S
with
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For PM we have
For FM we have
Under wideband condition and
Destination S/N for PM and FM
2
2 2 2/ ,where
/
x
D D x x
R
SS N S S
W S
2
2
3
2
// 3
3 3
x
D D
R
R
x x
D
f SS NW S
f SS D S
W W
2
3/
4
T
D D x
BS N S
W
1D Note that S
D/N
Dcan
be increased just byincreasing deviation!
2 3
( )
2 3
W
D FMW
R R
f WN df
S S
( )
2
W
WD PM
R R
WN df
S S
1,2( 2) 2
2 /(2 )
mT m f W
T
B f W
DW D B W
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FM post-detection S/N with deemphases
Deemphases filter (that is a lowpass filter connected afterdetector) can suppress noise further. FM post-detection noisePSD and total noise power without deemphases:
With deemphases filter (for simplification assume W/Bde>>1):
where
2
( )2
FM
R T
f fG f
S B
3
( )3
W
WD FM
R
WN G f df
S
3
2 2
/
( ) ( ) arctan /
de
W de
WD FM de de R
R de de
W B
B W WN G f H f df B W S
S B B2
21( )1 ( / )
de
de
H ff B
2 22
2/
/
x x R
D D x
de R de de
f S S S f fS N S
B W S W B B
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Example
FM radio
Without deemphases
With deemphases
Therefore if DSB or SSB system could be exchanged to FMsystem 640 fold transmission power savings could be achieved.Note, however that the required transmission bandwidth is nowabout 220 kHz /15 kHz = 15 times larger! Also, a problem is theFM threshold effect that we discuss next.
75 kHz, 15 kHz, 5, 1/ 2, 2.1kHz
x de
f W D S B
2
21 2
/ 3
(3 5 ) 38
D D xS N D S
2
/ ( / ) 640
D D de x
S N f B S
R
S
W
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Comparison of carrier wave
modulation systems